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EL2160
Data Sheet September 26, 2001 FN7051
180MHz Current Feedback Amplifier
The EL2160 is a current feedback operational amplifier with -3dB bandwidth of 130MHz at a gain of +2. Built using the Elantec proprietary monolithic complementary bipolar process, this amplifier uses current mode feedback to achieve more bandwidth at a given gain than a conventional voltage feedback operational amplifier. The EL2160 is designed to drive a double terminated 75 coax cable to video levels. Differential gain and phase are excellent when driving both loads of 500 (<0.01%/<0.01) and double terminated 75 cables (0.025%/0.1). The amplifier can operate on any supply voltage from 4V (2V) to 33V (16.5V), yet consume only 8.5mA at any supply voltage. Using industry-standard pinouts, the EL2160 is available in 8-pin PDIP and SO packages, as well as a 16-pin SO (0.300") package. All are specified for operation over the full -40C to +85C temperature range. For dual and quad applications, please see the EL2260/EL2460 datasheet.
Features
* 130MHz 3dB bandwidth (AV=+2) * 180MHz 3dB bandwidth (AV=+1) * 0.01% differential gain, RL=500 * 0.01 differential phase, RL=500 * Low supply current, 8.5mA * Wide supply range, 2V to 15V * 80mA output current (peak) * Low cost * 1500V/s slew rate * Input common mode range to within 1.5V of supplies * 35ns settling time to 0.1%
Applications
* Video amplifiers * Cable drivers
Ordering Information
PART NUMBER EL2160CN EL2160CS-T7 EL2160CS-T13 EL2160CM PACKAGE 8-Pin PDIP 8-Pin SO 8-Pin SO 16-Pin SO (0.300") TAPE & REEL 7" 13" 13" PKG. NO. MDP0031 MDP0027 MDP0027 MDP0027 MDP0027
* RGB amplifiers * Test equipment amplifiers * Current to voltage converters
EL2160CM-T13 16-Pin SO (0.300")
Pinouts
EL2160 (8-PIN PDIP, SO) TOP VIEW
EL2160 [16-PIN SO (0.300")] TOP VIEW
NC 1 NC 2 -IN 3 NC 4 +IN 5 NC 6 VS- 7 NC 8 +
16 NC 15 NC 14 VS+ 13 NC 12 OUT 11 NC 10 NC 9 NC
NC 1 -IN 2 +IN 3 VS- 4 +
8 NC 7 VS+ 6 OUT 5 NC
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2003. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners.
EL2160
Absolute Maximum Ratings (TA = 25C)
Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . . . . . . .+33V Voltage between +IN and -IN . . . . . . . . . . . . . . . . . . . . . . . . . . . .6V Current into +IN or -IN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10mA Internal Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . See Curves Operating Ambient Temperature Range . . . . . . . . . .-40C to +85C Operating Junction Temperature Plastic Packages . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150C Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 50mA Storage Temperature Range . . . . . . . . . . . . . . . . . .-65C to +150C
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Open-Loop DC Electrical Specifications
PARAMETER VOS TC VOS +IIN -IIN CMRR -ICMR PSRR -IPSR ROL DESCRIPTION Input Offset Voltage Average Offset Voltage Drift (Note 1) +Input Current -Input Current Common Mode Rejection Ratio (Note 2)
VS = 15V, RL = 150, TA = 25C unless otherwise specified. LIMITS CONDITIONS VS = 5V, 15V TEMP 25C Full VS = 5V, 15V VS = 5V, 15V VS = 5V, 15V 25C 25C 25C 25C 25C 25C VS = 15V RL = 400 VS = 5V RL = 150 25C 25C 25C 25C VS = 15V VS = 5V 25C 25C 25C 25C 25C 25C 3.0 60 12 500 500 1.5 75 50 MIN TYP 2 10 0.5 5 55 0.2 95 0.2 2000 1800 3.0 2.5 13.5 3.5 13.5 12 3.7 100 150 5 5 5 25 MAX 10 UNIT mV V/C A A dB A/V dB A/V k k M pF V V V V V mA
-Input Current Common Mode Rejection (Note 2) VS = 5V, 15V Power Supply Rejection Ratio (Note 3) -Input Current Power Supply Rejection (Note 3) Transimpedance (Note 4)
+RIN +CIN CMIR
+Input Resistance +Input Capacitance Common Mode Input Range
VO
Output Voltage Swing
RL = 400 VS =15V RL = 150 VS =15V RL = 150 VS =5V
ISC
Output Short Circuit Current (Note 5)
VS = 5V, VS = 15V
IS
Supply Current
VS = 15V VS = 5V
25C 25C
8.5 6.4
12.0 9.5
mA mA
NOTES: 1. Measured from TMIN to TMAX 2. VCM = 10V for VS = 15V and TA = 25C, VCM = 3V for VS = 5V and TA = 25C 3. The supplies are moved from 2.5V to 15V 4. VOUT = 7V for VS = 15V, and VOUT = 2V for VS = 5V 5. A heat sink is required to keep junction temperature below absolute maximum when an output is shorted
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EL2160
Closed-Loop AC Electrical Specifications
PARAMETER BW DESCRIPTION -3dB Bandwidth (Note 1) VS = 15V, AV = +2, RF = 560, RL = 150, TA = 25C unless otherwise noted. LIMITS CONDITIONS VS = 15V, AV = +2 VS = 15V, AV = +1 VS = 5V, AV = +2 VS = 5V, AV = +1 SR Slew Rate (Note 1)(Note 2) RL = 400 RF = 1k, RG = 110 RL = 400 t R , tF tPD OS tS dG Rise Time, Fall Time (Note 1) Propagation Delay (Note 1) Overshoot (Note 1) 0.1% Settling Time (Note 1) Differential Gain (Note 1)(Note 3) VOUT = 500mV VOUT = 10V AV = -1, RL = 1k RL = 150 RL = 500 dP Differential Phase (Note 1)(Note 3) RL = 150 RL = 500 NOTES: 1. All AC tests are performed on a "warmed up" part, except for Slew Rate, which is pulse tested 2. Slew Rate is with VOUT from +10V to -10V and measured at the 25% and 75% points 3. DC offset from -0.714V through +0.714V, AC amplitude 286mVP-P, f = 3.58MHz VOUT = 500mV 1000 MIN TYP 130 180 100 110 1500 1500 MAX UNIT MHz MHz MHz MHz V/s V/s
2.7 3.2 0 35 0.025 0.006 0.1 0.005
ns ns % ns % %
3
EL2160 Typical Performance Curves
Non-Inverting Frequency Response (Gain) Non-Inverting Frequency Response (Phase) Frequency Response for Various RL
Inverting Frequency Response (Gain)
Inverting Frequency Response (Phase)
Frequency Response for Various RF and RG
R
3dB Bandwidth vs Supply Voltage for AV = -1
Peaking vs Supply Voltage for AV = -1
3dB Bandwidth vs Temperature for AV = - 1
4
EL2160 Typical Performance Curves
3dB Bandwidth vs Supply Voltage for AV = +1
(Continued)
Peaking vs Supply Voltage for AV = +1
3dB Bandwidth vs Temperature for AV = +1
3dB Bandwidth vs Supply Voltage for AV = +2
Peaking vs Supply Voltage for AV = +2
3dB Bandwidth vs Temperature for AV = +2
3dB Bandwidth vs Supply Voltage for AV = +10
Peaking vs Supply Voltage for AV = +10
3dB Bandwidth vs Temperature for AV = +10
5
EL2160 Typical Performance Curves
Frequency Response for Various CL
(Continued)
Frequency Response for Various CIN-
PSRR and CMRR vs Frequency
2nd and 3rd Harmonic Distortion vs Frequency
Transimpedance (ROL) vs Frequency
Voltage and Current Noise vs Frequency
Closed-Loop Output Impedance vs Frequency
Transimpedance (ROL) vs Die Temperature
6
EL2160 Typical Performance Curves
Offset Voltage vs Die Temperature (4 Samples)
(Continued)
Supply Current vs Die Temperature
Supply Current vs Supply Voltage
+Input Resistance vs Die Temperature
Input Current vs Die Temperature
+Input Bias Current vs Input Voltage
Output Voltage Swing vs Die Temperature
Short Circuit Current vs Die Temperature
PSRR & CMRR vs Die Temperature
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EL2160 Typical Performance Curves
Differential Gain vs DC Input Voltage, RL = 150
(Continued)
Differential Phase vs DC Input Voltage, RL = 150
Small Signal Pulse Response
Differential Gain vs DC Input Voltage, RL = 500
Differential Phase vs DC Input Voltage, RL = 500
Large Signal Pulse Response
Slew Rate vs Supply Voltage
Slew Rate vs Temperature
Settling Time vs Settling Accuracy
8
EL2160 Typical Performance Curves
(Continued)
Long Term Settling Error 1.6 1.4
Package Power Dissipation vs Ambient Temp. JEDEC JESD51-3 Low Effective Thermal Conductivity Test Board 1.344W SO16 (0.300") JA=93C/W PDIP8 JA=100C/W 781mW SO8 JA=160C/W
Power Dissipation (W)
1.2 1.250W 1 0.8 0.6 0.4 0.2 0 0 25
50
75 85 100
125
150
Ambient Temperature (C)
Burn-In Circuit
EL2160
9
EL2160 Differential Gain and Phase Test Circuit
Simplified Schematic (One Amplifier)
Applications Information
Product Description
The EL2160 is a current mode feedback amplifier that offers wide bandwidth and good video specifications at a moderately low supply current. It is built using Elantec's proprietary complimentary bipolar process and is offered in industry standard pin-outs. Due to the current feedback architecture, the EL2160 closed-loop 3dB bandwidth is dependent on the value of the feedback resistor. First the desired bandwidth is selected by choosing the feedback
resistor, RF, and then the gain is set by picking the gain resistor, RG. The curves at the beginning of the Typical Performance Curves section show the effect of varying both RF and RG. The 3dB bandwidth is somewhat dependent on the power supply voltage. As the supply voltage is decreased, internal junction capacitances increase, causing a reduction in closed loop bandwidth. To compensate for this, smaller values of feedback resistor can be used at lower supply voltages.
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EL2160
Power Supply Bypassing and Printed Circuit Board Layout
As with any high frequency device, good printed circuit board layout is necessary for optimum performance. Ground plane construction is highly recommended. Lead lengths should be as short as possible, below 1/4". The power supply pins must be well bypassed to reduce the risk of oscillation. A 1.0F tantalum capacitor in parallel with a 0.01F ceramic capacitor is adequate for each supply pin. For good AC performance, parasitic capacitances should be kept to a minimum, especially at the inverting input (see Capacitance at the Inverting Input section). This implies keeping the ground plane away from this pin. Carbon resistors are acceptable, while use of wire-wound resistors should not be used because of their parasitic inductance. Similarly, capacitors should be low inductance for best performance. Use of sockets, particularly for the SO package, should be avoided. Sockets add parasitic inductance and capacitance which will result in peaking and overshoot.
Bandwidth vs Temperature
Whereas many amplifier's supply current and consequently 3dB bandwidth drop off at high temperature, the EL2160 was designed to have little supply current variations with temperature. An immediate benefit from this is that the 3dB bandwidth does not drop off drastically with temperature. With VS = 15V and AV = +2, the bandwidth only varies from 150MHz to 110MHz over the entire die junction temperature range of 0C < T < 150C.
Supply Voltage Range
The EL2160 has been designed to operate with supply voltages from 2V to 15V. Optimum bandwidth, slew rate, and video characteristics are obtained at higher supply voltages. However, at 2V supplies, the 3dB bandwidth at AV = +2 is a respectable 70MHz. The following figure is an oscilloscope plot of the EL2160 at 2V supplies, AV = +2, RF = RG = 560, driving a load of 150, showing a clean 600mV signal at the output.
Capacitance at the Inverting Input
Due to the topology of the current feedback amplifier, stray capacitance at the inverting input will affect the AC and transient performance of the EL2160 when operating in the non-inverting configuration. The characteristic curve of gain vs. frequency with variations of CIN- emphasizes this effect. The curve illustrates how the bandwidth can be extended to beyond 200MHz with some additional peaking with an additional 2pF of capacitance at the VIN- pin for the case of AV = +2. Higher values of capacitance will be required to obtain similar effects at higher gains. In the inverting gain mode, added capacitance at the inverting input has little effect since this point is at a virtual ground and stray capacitance is therefore not "seen" by the amplifier.
If a single supply is desired, values from +4V to +30V can be used as long as the input common mode range is not exceeded. When using a single supply, be sure to either 1) DC bias the inputs at an appropriate common mode voltage and AC couple the signal, or 2) ensure the driving signal is within the common mode range of the EL2160.
Feedback Resistor Values
The EL2160 has been designed and specified with RF = 560 for AV = +2. This value of feedback resistor yields extremely flat frequency response with little to no peaking out to 130MHz. As is the case with all current feedback amplifiers, wider bandwidth, at the expense of slight peaking, can be obtained by reducing the value of the feedback resistor. Inversely, larger values of feedback resistor will cause rolloff to occur at a lower frequency. By reducing RF to 430, bandwidth can be extended to 170MHz with under 1dB of peaking. Further reduction of RF to 360 increases the bandwidth to 195MHz with about 2.5dB of peaking. See the curves in the Typical Performance Curves section which show 3dB bandwidth and peaking vs. frequency for various feedback resistors and various supply voltages.
Settling Characteristics
The EL2160 offers superb settling characteristics to 0.1%, typically in the 35ns to 40ns range. There are no aberrations created from the input stage which often cause longer settling times in other current feedback amplifiers. The EL2160 is not slew rate limited, therefore any size step up to 10V gives approximately the same settling time. As can be seen from the Long Term Settling Error curve, for AV = +1, there is approximately a 0.035% residual which tails away to 0.01% in about 40s. This is a thermal settling error caused by a power dissipation differential (before and after the voltage step). For AV = -1, due to the inverting mode configuration, this tail does not appear since the input stage does not experience the large voltage change as in the non-inverting mode. With AV = -1, 0.01% settling time is slightly greater than 100ns.
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EL2160
Power Dissipation
The EL2160 amplifier combines both high speed and large output current drive capability at a moderate supply current in very small packages. It is possible to exceed the maximum junction temperature allowed under certain supply voltage, temperature, and loading conditions. To ensure that the EL2160 remains within its absolute maximum ratings, the following discussion will help to avoid exceeding the maximum junction temperature. The maximum power dissipation allowed in a package is determined by its thermal resistance and the amount of temperature rise according to:
T JMAX - T AMAX P DMAX = ------------------------------------------- JA
packages. The curves assume worst case conditions of TA = +85C and IS = 11mA.
Supply Voltage vs RLOAD for Various VOUT (8-Pin SO Package)
The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage plus the power in the IC due to the load, or:
V OUT P DMAX = 2 x V S + ( V S - V OUT ) x --------------RL
Supply Voltage vs RLOAD for Various VOUT (PDIP Package)
where IS is the supply current. (To be more accurate, the quiescent supply current flowing in the output driver transistor should be subtracted from the first term because, under loading and due to the class AB nature of the output stage, the output driver current is now included in the second term.) In general, an amplifier's AC performance degrades at higher operating temperature and lower supply current. Unlike some amplifiers, the EL2160 maintains almost constant supply current over temperature so that AC performance is not degraded as much over the entire operating temperature range. Of course, this increase in performance doesn't come for free. Since the current has increased, supply voltages must be limited so that maximum power ratings are not exceeded. The EL2160 consumes typically 8.5mA and maximum 11.0mA. The worst case power in an IC occurs when the output voltage is at half supply, if it can go that far, or its maximum values if it cannot reach half supply. If we set the two PDMAX equations equal to each other, and solve for VS, we can get a family of curves for various loads and output voltages according to:
R L x ( T MAX -T AMAX ) V S = -------------------------------------------------------- + ( V OUT ) / [ ( 2 x I S x R L ) + V OUT ] JA
The curves do not include heat removal or forcing air, or the simple fact that the package will probably be attached to a circuit board, which can also provide some form of heat removal. Larger temperature and voltage ranges are possible with heat removal and forcing air past the part.
Current Limit
The EL2160 has an internal current limit that protects the circuit in the event of the output being shorted to ground. This limit is set at 100mA nominally and reduces with junction temperature. At a junction temperature of 150C, the current limits at about 65mA. If the output is shorted to ground, the power dissipation could be well over 1W. Heat removal is required in order for the EL2160 to survive an indefinite short.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back termination series resistor will decouple the EL2160 from the capacitive cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without termination resistors. In these applications, an additional small value (5-50) resistor in series with the output will eliminate most peaking.
The following curves show supply voltage (VS) vs RLOAD for various output voltage swings for the 2 different
12
EL2160
The gain resistor, RG, can be chosen to make up for the gain loss created by this additional series resistor at the output.
EL2160 Macromodel
* Revision A, November 1993 * AC Characteristics used CIN- (pin 2) = 1 pF; RF = 560 * Connections: +input * | -input * | | +Vsupply * | | | -Vsupply * | | | | output * | | | | | .subckt EL2160/EL 3 2 7 4 6 * * Input Stage * e1 10 0 3 0 1.0 vis 10 9 0V h2 9 12 vxx 1.0 r1 2 11 130 l1 11 12 25nH iinp 3 0 0.5A iinm 2 0 5A r12 3 0 2Meg * * Slew Rate Limiting * h1 13 0 vis 600 r2 13 14 1K d1 14 0 dclamp d2 0 14 dclamp * * High Frequency Pole * *e2 30 0 14 0 0.00166666666 l3 30 17 0.43H c5 17 0 0.27pF r5 17 0 500 * * Transimpedance Stage * g1 0 18 17 0 1.0 ro1 18 0 2Meg cdp 18 0 2.285pF * * Output Stage * q1 4 18 19 qp q2 7 18 20 qn q3 7 19 21 qn q4 4 20 22 qp r7 21 6 4 r8 22 6 4 ios1 7 19 2mA ios2 20 4 2mA * * Supply Current * ips 7 4 3mA *
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EL2160
* Error Terms * ivos 0 23 2mA vxx 23 0 0V e4 24 0 3 0 1.0 e5 25 0 7 0 1.0 e6 26 0 4 0 1.0 r9 24 23 562 r10 25 23 1K r11 26 23 1K * * Models * .model qn npn (is=5e-15 bf=100 tf=0.1ns) .model qp pnp (is=5e-15 bf=100 tf=0.1ns) .model dclamp d (is=1e-30 ibv=0.266 bv=2.24 n=4) .ends
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